Rev 1.2
DIO61845
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for
Power Meters
Features
Descriptions
Operating Input Range: 5V to 40V
The DIO61845 is a high-frequency, step-down,
Adjustable Output Range: 0.8V to 0.95∙VIN
switching regulator with integrated high-side and
Operating Quiescent Current: 150μA
low-side power MOSFET designed specifically for
Fixed Switching Frequency: 2MHz
power meter applications. The DIO61845 can
400mΩ/200mΩ Internal Power MOSFETs
provide up to 0.6A output current and current
Optimized for Power Meter Applications
mode control for fast loop response.
Satisfies 0.1% Output Voltage Ripple
The wide input range of 5V to 40V is suitable for
Requirements in Power Meter Applications
various power meter step-down applications.
Low Dropout Mode
Quiescent current of 10μA shutdown mode allows
Light-Load Mode
devices to be used for battery power supply
>90% Efficiency
applications. The DIO61845 uses high duty cycle
Dedicated Internal Compensation
and low dropout mode under the condition of low
Stable with Ceramic/Electrolytic Output
input voltage of power meter.
Capacitors
The DIO61845 achieves high power conversion
Internal Soft Start (SS)
efficiency in a wide load range by reducing
Precision Current Limit without Current
switching frequency under light load conditions to
Sensing Resistor
reduce switching and gate drive losses.
Guaranteed Industrial Temperature Range
Frequency folding prevents short circuit and
Limits
inductance current from losing control during
Package: SOT23-6
startup. Thermal shutdown provides reliable and
fault-tolerant
Applications
operation.
The
DIO61845
is
packaged in SOT23-6.
Power Meters Only
Typical Application
C3
0.1μF
C3
BST
SW
22μH
C4
VIN
C2
R3
100kΩ
FB
107kΩ
1.5MΩ
R2
R1
C
0.1μF
C5
+
470μF
GND
C1
10μF
VIN
BST
SW
GND
VIN
FB
EN
4. 7μF
10μH
C2
R3
100kΩ
EN
Pow er Meter 12V Output Rail, 0.6A Load
VOUT
5V/0.6A
L1
C6
0.1μ F
Opt.
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0.1μF
VOUT
12V/0.6A
L1
10.7kΩ
0.1μF
C5
10μF
C1
C6
0.1μF
VIN
4.7μ F
56kΩ
R2
R1
C
Opt.
Pow er Meter 5V Output Rail, 0.6A Load
© 2021 DIOO MICROCIRCUITS CO., LTD
DIO61845• Rev. 1.2
DIO61845
Order Part
Top Marking
Number
DIO61845ST6
DAYW
TA
Green
Package
-40 to 85°C
SOT23-6
Tape & Reel, 3000
Pin Assignment
SOT23-6
BST 1
6 SW
GND 2
5
VIN
FB 3
4
EN
Figure 1 Top View
Pin Descriptions
Pin Name
BST
GND
Description
Bootstrap. Positive power supply for the internal, floating, high-side MOSFET driver.
Connect a bypass capacitor between BST and SW.
Ground. Connect an output capacitor as close to GND as possible. Avoid routing GND
near high-current switch paths.
Feedback. FB is the input to the error amplifier. Connect FB to an external resistor
FB
divider between the output and GND. Compare FB against the internal 0.8V reference
to set the regulation voltage.
EN
Enable input. Pull EN below the specified threshold to shut the chip down. Pull EN
above the specified threshold to enable the chip. Float EN to disable the chip.
Input supply. VIN supplies power to the internal control circuitry, both BST regulators,
VIN
and the high-side switch. Place a decoupling capacitor to ground close to VIN to reduce
switching spikes.
SW
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Switch node. SW is the output of the high-side switch.
© 2021 DIOO MICROCIRCUITS CO., LTD
DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Ordering Information
DIO61845
Stresses beyond those listed under “Absolute Maximum Rating” may cause permanent damage to the device. These are stress
ratings only and functional operation of the device at these or any other condition beyond those indicated in the operational sections
of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
Parameter
Rating
Unit
Supply voltage
VIN
-0.3 to 42
V
Switch voltage
VSW
-0.3 to (VIN + 0.3)
V
BST to SW
-0.3 to 6.0
V
All other pins
-0.3 to 6.0
V
Continuous power dissipation (TA = 25°C) (1)
0.6
W
Junction temperature
150
°C
Lead temperature
260
°C
-65 to 150
°C
Storage temperature
ӨJA
170
ӨJC
130
Human Body Mode
1500
V
300
mA
Package Thermal Resistance
ESD
°C/W
Latch up
Note:
1. The maximum allowable power dissipation is a function of the maximum junction temperature TJ(MAX), the
junction-to-ambient
thermal resistance θJA, and the ambient temperature TA. The maximum allowable continuous power dissipation at any ambient
temperature is calculated by PD(MAX)=(TJ(MAX)-TA)/θJA. Exceeding the maximum allowable power dissipation produces an excessive
die temperature, and the regulator goes into thermal shutdown. Internal thermal shutdown circuitry protects the device from permanent
damage.
Recommend Operating Conditions
The Recommended Operating Conditions table defines the conditions for actual device operation. Recommended Operating
conditions are specified to ensure optimal performance to the datasheet specifications. DIOO does not Recommend exceeding them
or designing to Absolute Maximum Ratings.
Parameter
Rating
Unit
Supply voltage
VIN
5 to 40
V
Output voltage
VOUT
Adjustable from 0.8
V
Operating junction temperature
TJ
-40 to 125
°C
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© 2021 DIOO MICROCIRCUITS CO., LTD
DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Absolute Maximum Ratings
DIO61845
VIN = 24V, VEN = 2V, TJ = -40°C to 125°C (2), unless otherwise noted. Typical values at TJ = 25°C.
Symbol
VFB
Parameter
Conditions
Min.
Typ.
Max.
TJ = -40°C to 125°C
0.78
0.8
0.82
TJ = 25°C
0.788
0.8
0.812
Feedback voltage
V
Feedback bias current
RON_HS
High-side switch on resistance
RON_LS
Low-side switch on resistance
High-side switch leakage
VBST - VSW = 5V
0.1
μA
400
800
mΩ
200
400
mΩ
1
μA
1
μA
VEN = 0V, VSW = 0V
Low-side switch leakage
ILIM
Unit
Current limit
0.8
1.0
1.2
A
VIN UVLO rising threshold
4.35
4.6
4.85
V
VIN UVLO falling threshold
3.65
3.9
4.15
V
VIN UVLO hysteresis
Soft-start time
0.7
VFB from 10% to 90%
0.5
1
ms
2
2.4
MHz
fSW
Oscillator frequency
tON
Minimum switch on time (3)
IS
Shutdown supply current
VEN < 0.3V
10
15
μA
IQ
Quiescent supply current
No load, VFB = 0.83V, no switching
150
350
µA
VIH
1.6
V
100
ns
Thermal shutdown (3)
175
°C
Thermal shutdown hysteresis (3)
30
°C
Enable rising threshold
Low to high
Enable falling threshold
Enable threshold hysteresis
1.62
1.8
1.98
V
1.395
1.55
1.705
V
250
mV
Note:
2. Not tested in production and guaranteed by over-temperature correlation.
3. Not tested in production and derived from bench characterization.
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© 2021 DIOO MICROCIRCUITS CO., LTD
DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Electrical Characteristics
DIO61845
VIN
1.7MΩ
EN
INTERNAL
REGULA TO R
REFERENCE
UVLO
V CC
7.5V
BST
0.5ms SS
SS
CLK
Oscillator
ISW
3.2pF
Control
Log ic
ISW
SW
V CC
50pF 850k Ω
100kΩ
FB
SS
0.8 V
Comp
GND
OPERATION
The DIO61845 is a 2MHz, synchronous, step- down, switching regulator with integrated high-side and low-side
power MOSFETs. The DIO61845 provides an internally compensated, highly efficient output of up to 0.6A with
current- mode control and also features a wide input voltage range, internal soft-start control, and a precision
current limit. Its very low operational quiescent current makes it suitable for battery-powered applications.
Pulse-Width Modulation (PWM) Control
At moderate-to-high output currents, the DIO61845 operates in a fixed-frequency, peak-current-control mode to
regulate the output voltage. A pulse-width modulation (PWM) cycle initiated by the internal clock turns on the
power high-side MOSFET (HS-FET). The HS-FET remains on until its current reaches the value set by the COMP
voltage (VCOMP). After the HS-FET is off, the low-side MOSFET (LS-FET) turns on, and the inductor current flows
through the LS-FET. To avoid a shoot-though, a dead time is inserted to prevent the HS-FET and LS-FET from
turning on at the same time. For each turn- on and turn-off in a switching cycle, the HS-FET turns on and off with
a minimum on and off time limit.
To prevent inductor current and output voltage runaway, the switching frequency folds back when the HS-FET
minimum turn-on is detected internally.
When the PWM signal goes low, the HS-FET turns off and remains off for at least 100ns before the next cycle
begins. If the current in the HS-FET does not reach the COMP-set current value within one PWM cycle, the HSFET remains on to avoid a turn-off operation.
Pulse-Skipping Mode (PSM)
Under light-load conditions, the DIO61845 enters pulse-skipping mode (PSM) to improve efficiency. PSM is
triggered when VCOMP drops below the internal sleep threshold, which generates a pause command to block the
turn- on clock pulse, so the power MOSFET does not turn on. This reduces gate driving and switching losses.
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Block Diagram
DIO61845
load efficiency.
When VCOMP exceeds the sleep threshold, the pause signal resets, and the chip resumes normal PWM operation.
Whenever the pause command changes from low to high, the PWM signal goes high immediately and turns on
the power MOSFET.
Error Amplifier (EA)
The error amplifier is composed of an internal op-amp with an R-C feedback network connected between its
output node (internal COMP node) and its negative input node (FB). When the FB voltage (VFB) drops below the
internal reference voltage (VREF), the op-amp drives the COMP output high, producing a higher switch peak current
output and delivering more energy to the output. Conversely, when VFB rises above VREF, the switch peak current
output drops.
Connect FB to the tap of a voltage divider connected between VOUT and GND composed of R1 and R2. R1 also
serves to control the gain of the error amplifier in addition to the internal compensation R-C network.
Internal Regulator
The 2.6V internal regulator powers most of the internal circuitry. This regulator takes the VIN input and operates
in the full VIN range. When VIN is greater than 3.0V, the output of the regulator is in full regulation. When VIN drops
below 3.0V, the output degrades.
Enable Control (EN)
The DIO61845 has a dedicated enable control pin (EN). When VIN rises above the threshold, EN can enable or
disable the chip for high effective logic. Its falling threshold is 1.55V, and its rising threshold is about 1.8V. An
internal 1.7MΩ resistor from EN to GND allows EN to be floated to shut down the chip.
When the EN voltage is pulled to 0V, the chip enters the lowest shutdown current mode. When the EN voltage
rises above 0V but remains below the rising threshold, the chip remains in shutdown mode with a slightly higher
shutdown current.
EN is clamped internally using a 7.5V series Zener diode. Connecting the EN input through a pull-up resistor to
VIN limits the EN input current below 100μA. For example, with 12V connected to VIN, RPULLUP≥(12V7.5V)÷100μA=45kΩ.
Connecting EN to a voltage source directly without a pull-up resistor requires limiting the amplitude of the voltage
source to ≤6V to prevent damage to the Zener diode.
Under-Voltage Lockout (UVLO)
VIN under-voltage lockout (UVLO) protects the chip from operating at an insufficient supply voltage. The UVLO
rising threshold is approximately 4.6V, while its falling threshold is 3.9V.
Internal Soft Start (SS)
A reference-type soft start (SS) prevents the converter output voltage from overshooting during start-up. When
the chip starts up, the internal circuitry generates a soft-start voltage (VSS) that ramps up from 0V during the SS
time. When VSS is lower than VREF, VSS overrides VREF as the error amplifier reference.
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
The pause command causes the entire chip to enter sleep mode, reducing the quiescent current to improve light-
DIO61845
voltage overshoot.
Thermal Shutdown
Thermal shutdown prevents thermal runaway. When the silicon die temperature exceeds its upper threshold, the
entire chip shuts down. When the temperature drops below its lower threshold, the chip is enabled again.
Floating Driver and Bootstrap Charging
The floating power MOSFET driver is powered by an external bootstrap capacitor. This floating driver has its own
UVLO protection with a rising threshold of about 2.4V and a falling threshold of about 300mV. During UVLO, VSS
resets to zero. When the UVLO ends, the controller enters soft start.
The bootstrap capacitor is charged and regulated to about 5V by the dedicated internal bootstrap regulator. And
it will stop charging the bootstrap capacitor when DIO61845 enters pulses-skipping mode, so probe the BS node
is forbidden to avoid discharging the bootstrap capacitor.
Current Comparator and Current Limit
A current-sense MOSFET senses the power MOSFET current. This current is input to the high-speed current
comparator for current-mode control. When the power MOSFET turns on, the comparator is first blanked to limit
noise, and then compares the power switch current against VCOMP. When the sensed value exceeds VCOMP, the
comparator output goes low to turn off the power MOSFET. The maximum current of the internal power MOSFET
is limited cycle-by-cycle internally. The switching frequency folds back to prevent an inductor current runaway
during start-up or a short circuit.
Low Dropout Operation
The DIO61845 is designed to operate at almost 100% duty cycle to improve dropout. When the current in the HSFET does not reach the COMP-set current value within one PWM cycle, the HS-FET remains on to prevent a
turn-off operation. The HS-FET can remain on for a maximum of 15µs and then turns off for a minimum of 160ns.
To prevent the voltage across BST to SW from dropping too low during the low dropout operation, the current
comparator enters power-save mode, in which the speed is degraded. This reduces the bootstrap capacitor
current consumption when HS-FET turns on for longer than 2µs. Therefore, the voltage across the bootstrap
capacitor can remain at a high level (close to 5V).
Start-Up and Shutdown
If both VIN and VEN exceed their respective thresholds, the chip starts up. The reference block first starts to
generate a stable reference voltage and current, and then the internal regulator starts to provide a stable supply
for the rest of the circuit.
While the internal supply rail is up, an internal timer turns the power MOSFET off for about 50µs to blank any
start-up noise. When the internal soft-start block is enabled, it first holds its SS output low to ensure that the rest
of the circuit is ready before ramping up.
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
The maximum VSS value is approximately the same as VFB, so if VFB falls, the maximum of VSS falls. This
accommodates short-circuit recovery. When the short circuit is removed, VSS ramps up to prevent an output
DIO61845
low. The floating driver is not subject to this shutdown command, but its charging path is disabled.
Application Information
Setting the Output Voltage
Set the output voltage of DIO61845 by using a resistor divider (see Figure 2):
DIO618 45
R1
FB
V OUT
R2
Figure 2 FB Resistor Divider to Set VOUT
Calculate the output voltage with Equation (1):
VOUT = VFB *
( R1 + R 2)
R2
(1)
The feedback resistor (R1) also sets the feedback loop bandwidth with the internal compensation network.
To achieve optimal stability performance and transient response, choose R1 to be around 1.5MΩ in power meter
applications with a 12V output rail. Set R1 to be 56kΩ for 5V output rail applications. Then, calculate R2 with
Equation (2):
R2 =
R1
VOUT
−1
0 .8V
(2)
Table 1 lists the recommended feedback resistor values for common output voltages.
Table 1 Resistor Selection vs. Output Voltage Setting
VOUT
R1
R2
5V
56kΩ (1%)
10.7kΩ (1%)
12V
1.5MΩ (1%)
107kΩ (1%)
Selecting the Inductor
The inductor supplies constant current to the output load while being driven by the switched input voltage. A
larger-value inductor results in less ripple current and a lower output ripple voltage but also has a larger physical
size, higher series resistance, and lower saturation current.
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© 2021 DIOO MICROCIRCUITS CO., LTD
DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Three events can shut down the chip: EN low, VIN low, and thermal shutdown. During the shutdown procedure,
the signaling path is blocked first to avoid any fault triggering. VCOMP and the internal supply rail are then pulled
DIO61845
inductance value can be calculated with Equation (3):
L1 =
VOUT
V
* (1 − OUT )
f S *△I L
VIN
(3)
Where VOUT is the output voltage, VIN is the input voltage, fS is the switching frequency, and ∆IL is the peak-topeak inductor ripple current.
Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current
can be calculated with Equation (4):
I LP = I LOAD +
VOUT
V
* (1 − OUT )
2 * f S * L1
VIN
(4)
Where ILOAD is the load current.
Additionally, the inductor value influences the DIO61845 load ability during start-up. When the output voltage
starts up, fS folds back the minimum to several tens of kHz. Based on Equation (4), a smaller L1 or a lower fS
leads to a higher ILP. Therefore, if a small inductor value is used (e.g.: 10μH inductor in a 5V output rail power
meter application), the current limit is reached when the DIO61845 starts up with a >250mA constant current load.
Then, the output voltage fails to be set up. In this case, for a >250mA constant current load with a 10µH inductor,
the DIO61845 must first start up with a load250mA load sufficiently.
Selecting the Input Capacitor
The input capacitor (C1) can be electrolytic, tantalum, or ceramic. When using electrolytic or tantalum capacitors,
add a small, high-quality, ceramic capacitor (C2) (e.g.: 0.1μF) as close to the IC as possible. When using ceramic
capacitors, ensure that they have enough capacitance to provide a sufficient charge to prevent excessive voltage
ripple at the input.
The input voltage ripple caused by the capacitance can be estimated with Equation (5):
△VIN =
I LOAD VOUT
V
*
* (1 − OUT )
f S * C1 VIN
VIN
(5)
Selecting the Output Capacitor
An output capacitor (C4) is required to maintain the DC output voltage. Ceramic, tantalum, or low ESR electrolytic
capacitors are recommended. Low ESR capacitors are recommended to keep the output voltage ripple low. The
output voltage ripple can be estimated with Equation (6):
△VOUT =
VOUT
V
1
* (1 − OUT ) * ( RESR +
)
fS * L
VIN
8 * fS * C 4
(6)
Where L is the inductor value, and RESR is the equivalent series resistance (ESR) value of the output capacitor.
In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance.
The output voltage ripple is caused mainly by the capacitance. For simplification, the output voltage ripple can be
estimated with Equation (7):
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
To determine the inductance, allow the peak-to- peak ripple current in the inductor to be approximately 30% of
the maximum load current and choose a peak inductor current below the maximum switch current limit. The
DIO61845
VOUT
2
8 * fS * L * C 4
* (1 −
VOUT
)
VIN
(7)
In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching
frequency.
For simplification, the output ripple can be approximated with Equation (8):
△VOUT =
VOUT
V
* (1 − OUT ) * RESR
fS * L
VIN
(8)
The characteristics of the output capacitor also affect the stability of the regulation system.
In power meter applications, the output capacitors are large-value electrolytic capacitors, typically, with an RESR
and capacitance with a large temperature variation. This large temperature variation changes the part’s feedback
loop, making it difficult to keep the loop stable over the full operation temperature, especially when the DIO61845
works in a deep dropout mode (VIN-VOUT25V, due to a low response speed of the current limit loop, there
is a risk that the inductor current will rush high when SCP enters with a special slew rate.
PCB Layout Guidelines
Efficient PCB layout requires high-frequency noise considerations to limit voltage spikes on the SW node.
1. Keep the path of the input decoupling capacitor, VIN, SW, and PGND as short as possible using short and wide
traces.
2. Keep the passive components as close to the device as possible.
3. Run the feedback trace far from the inductor and noisy power traces. If possible, run the feedback trace on the
opposite side of the PCB from the inductor, separated by a ground plane. Expect greater switching losses at high
switching frequencies.
4. Add a grid of thermal vias under the exposed pad to improve thermal conductivity.
5. Use small vias (15mil barrel diameter) so that the hole fills during the plating process and prevent solder wicking
during the reflow process associated with larger vias.
6. Use a pitch (distance between the centers) of approximately 40mil between the thermal vias.
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Table 2 Components Selection Guide
DIO61845
Figure 3. Quiescent Current vs. Junction Temperature
Figure 4. Vin UVLO vs. Junction Temperature
Figure 5. EN Threshold vs. Junction Temperature
Figure 6. Efficiency vs. Load Current
Iout=0.125A
Iout=0.4A
Figure 7. Output Voltage Ripple
Figure 8. Output Voltage Ripple
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Typical Performance Characteristic
DIO61845
Iout =0.6A
Figure 9. Steady State
Figure 10. Steady State
Iout=0A
Iout=0.6A
Figure 11. Start up through Vin
Figure 12. Start up through Vin
Iout=0A
Iout=0.6A
Figure 13. Shutdown through Vin
Figure 14. Shutdown through Vin
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Iout =0A
DIO61845
Iout=0.6A
Figure 15. Start up through EN
Figure 16. Start up through EN
Iout=0A
Iout=0A
Figure 17. Shutdown through EN
Figure 18. Shutdown through EN
Iout=0A to short circuit
Iout=0.6A to short circuit
Figure 19. SCP Entry
Figure 20. SCP Entry
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
Iout=0A
DIO61845
Figure 21. SCP Steady State
Figure 22. SCP Recovery
short circuit to Iout=0.6A
Iout=0.3A0.6A 1.6A/us
Figure 23. SCP Recovery
Figure 24. Load Transient
Iout=10mA0.6A 1.6A/us
Figure 25. Load Transient
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
short circuit to Iout=0A
DIO61845
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For additional product information, or full datasheet, please contact with our Sales Department or Representatives.
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DIO61845• Rev. 1.2
40V, 0.6A, 2MHz, Synchronous, Step-Down Converter for Power Meters
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